Wireless communication device, integrated circuitry, and wireless communication method

ABSTRACT

A wireless communication device has an analog control loop circuitry that generates an analog control signal to adjust a phase of a voltage controlled oscillation signal, in accordance with a phase of a reception signal, a digital control loop circuitry that generates a digital control signal having a frequency determined by a frequency of a reference signal and a predetermined frequency setting code signal and having a phase opposite to a phase of the analog control signal, a voltage controlled oscillator that generates the voltage controlled oscillation signal, on the basis of the analog control signal and the digital control signal, and a data slicer that generates a digital signal obtained by digital demodulation of the reception signal, on the basis of a comparison result of the digital control signal and a predetermined threshold value.

CROSS REFERENCE TO RELATED APPLICATIONS

This application is based upon and claims the benefit of priority fromthe prior Japanese application No. 2013-173844 filed on Aug. 23, 2013and the PCT application No. PCT/JP2014/072062, filed on Aug. 22, 2014,the entire contents of which are incorporated herein by reference.

FIELD

The present invention relates to a wireless communication device, anintegrated circuitry, and a wireless communication method.

BACKGROUND

An analog synchronous PSK/FSK demodulator according to the related artincludes a mixer to execute frequency conversion on an RF signalreceived by an antenna, a channel selection filter, and a voltagecontrolled oscillator (VCO) to supply a local oscillation signal to themixer and adopts a phase locked loop to supply a control voltage of theVCO from an output of the channel selection filter and lock phases of aVCO frequency and an RF signal frequency.

In this type of demodulator, when there is an interfering wave havinglarge power, the VCO is pulled in an interfering wave frequency, insteadof the RF signal frequency. Therefore, interfering wave resistance isnot sufficient. For example, even though it is considered that theinterfering wave is suppressed by a BPF disposed at a previous stage ofthe mixer, when the interfering wave frequency approaches an RF signal,an extraordinarily sharp cutoff characteristic that cannot be realizedin an external component is required. Therefore, a problem is notresolved.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram illustrating a schematic configuration of areceiver 1 according to a first embodiment;

FIGS. 2A and 2B are diagrams illustrating a demodulation principle of aBPSK signal;

FIG. 3 is a diagram illustrating an example of an internal configurationof a data slicer;

FIG. 4 is a block diagram illustrating a schematic configuration of areceiver 1 according to a second embodiment;

FIG. 5A is a diagram illustrating data included in a reception signal,FIG. 5B is a diagram illustrating an analog control signal V_(MIX) of ananalog control loop, FIG. 5C is a diagram illustrating a digital controlsignal D_(ctl) of a digital control loop, and FIG. 5D is a diagramillustrating a waveform of an output signal D′_(ctl) of a channelselection filter 30;

FIG. 6 is a block diagram illustrating an example of an IIR filter;

FIG. 7 is a block diagram illustrating an example of an FIR filter;

FIG. 8 is a block diagram illustrating a schematic configuration of areceiver 1 according to a third embodiment;

FIGS. 9A to 9C are timing diagrams when there is a frequency offsetbetween a reception signal and a VCO signal;

FIG. 10A is a diagram illustrating data of a reception signal in apreamble portion of the reception signal, FIG. 10B is a diagramillustrating an analog control signal V_(MIX) in the preamble portion,and FIG. 10C is a diagram illustrating a waveform of a digital controlsignal D_(ctl) in the preamble portion;

FIG. 11 is a diagram illustrating a phase-voltage characteristic of theanalog control signal V_(MIX);

FIG. 12 is a block diagram illustrating a schematic configuration of areceiver 1 according to a fourth embodiment;

FIG. 13 is a diagram illustrating a transfer characteristic of FIG. 12;

FIG. 14 is a block diagram illustrating a schematic configuration of areceiver 1 according to a fifth embodiment;

FIGS. 15A and 15B are waveform diagrams illustrating an operationprinciple of a phase shift unit 51;

FIG. 16 is a block diagram illustrating a schematic configuration of areceiver 1 according to a sixth embodiment;

FIG. 17 is a signal waveform diagram illustrating an operation accordingto the sixth embodiment;

FIG. 18 is a block diagram illustrating a schematic configuration of areceiver 1 according to a seventh embodiment;

FIG. 19 is a block diagram illustrating a schematic configuration of awireless communication device 71 according to an eighth embodiment;

FIG. 20 is a block diagram of a modification of FIG. 19;

FIG. 21 is a diagram illustrating an example of wireless communicationof a PC and a mouse; and

FIG. 22 is a diagram illustrating an example of wireless communicationof the PC and a wearable terminal.

DETAILED DESCRIPTION

A wireless communication device according to one embodiment has ananalog control loop circuitry that generates an analog control signal toadjust a phase of a voltage controlled oscillation signal, in accordancewith a phase of a reception signal, a digital control loop circuitrythat generates a digital control signal having a frequency determined bya frequency of a reference signal and a predetermined frequency settingcode signal and having a phase opposite to a phase of the analog controlsignal, a voltage controlled oscillator that generates the voltagecontrolled oscillation signal, on the basis of the analog control signaland the digital control signal, and a data slicer that generates adigital signal obtained by digital demodulation of the reception signal,on the basis of a comparison result of the digital control signal and apredetermined threshold value. Gain of the digital control loopcircuitry is higher than gain of the analog control loop circuitry.

Hereinafter, embodiments of the present invention will be described withreference to the drawings.

First Embodiment

FIG. 1 is a block diagram illustrating a schematic configuration of areceiver 1 in a wireless communication device according to a firstembodiment. The receiver 1 of FIG. 1 includes an analog control loopunit (analog control loop circuitry) 2, a digital control loop unit(digital control loop circuitry) 3, a voltage controlled oscillator 4,and a data slicer 5. The receiver 1 of FIG. 1 is used when a PSK signalis received, for example. The wireless communication device according tothe following embodiment may include only the receiver and may include aconfiguration other than the receiver, such as a transmitter. Inaddition, the wireless communication device may be a stationarycommunication device and may be a portable wireless terminal.

The analog control loop unit 2 generates an analog control signalV_(MIX) to adjust a phase of a voltage controlled oscillation signal, inaccordance with a phase of a reception signal received by an antenna 6.

The digital control loop unit 3 generates a digital control signalD_(ctl) that has a frequency determined by a frequency of a referencesignal and a predetermined frequency setting code signal, offsetsfluctuation of the phase of the voltage controlled oscillation signal,and has a phase opposite to a phase of the analog control signalV_(MIX).

The analog control loop unit 2 performs a tracking control so that afrequency of the voltage controlled oscillation signal follows thereception signal. Meanwhile, the digital control loop unit 3 preventsthe tracking control and instead performs a tracking control so that thefrequency of the voltage controlled oscillation signal matches a settingfrequency determined by the reference signal and the frequency settingcode signal. As a result of performing the opposite tracking controls,the analog control signal V_(MIX) generated by the analog control loopunit 2 and the digital control signal D_(ctl) generated by the digitalcontrol loop unit 3 become differential signals of which phases areopposite to each other.

The voltage controlled oscillator 4 (VCO) generates a voltage controlledoscillation signal (hereinafter, referred to as the VCO signal), on thebasis of the analog control signal V_(MIX) and the digital controlsignal D_(ctl).

The data slicer 5 compares the digital control signal D_(ctl) with apredetermined threshold value in synchronization with a reference signalCLK_(symbol) from a second reference signal source 21 and generates adigital signal in accordance with the reception signal. The digitalsignal is a signal obtained by digital demodulation of the receptionsignal and a digital demodulator does not need to be providedseparately.

The analog control loop unit 2 has a low noise amplifier 11, a frequencyconverter 12, and a low-pass filter 13. The low noise amplifier 11amplifies the reception signal received by the antenna 6. The frequencyconverter 12 generates a phase difference signal of the reception signaland the VCO signal. The low-pass filter 13 removes an unnecessary highfrequency component included in an output signal of the frequencyconverter 12 and generates the analog control signal V_(MIX).

The digital control loop unit 3 has a first reference signal source 20,the second reference signal source 21, a phase-digital converter (TDC:time-to-digital converter) 22, a binary counter 23, a digital adder 24,a digital differentiator 25, a digital subtracter 26, and a loop gaincontrol unit (loop gain controller) 27.

The phase-digital converter 22 detects a phase of the VCO signal insynchronization with a reference signal F_(REF) from the first referencesignal source 20. The binary counter 23 executes a count operation insynchronization with a rising edge of the VCO signal.

The digital adder 24 adds an output signal of the phase-digitalconverter 22 and a count signal of the binary counter 23 and detects thephase of the VCO signal. Because the binary counter 23 measures thephase of the VCO signal roughly and the phase-digital converter 22measures the phase of the VCO signal finely, the phase of the VCO signalcan be detected by adding output signals of the phase-digital converter22 and the binary counter 23 by the digital adder 24.

The digital differentiator 25 performs differentiation processing on anoutput signal of the digital adder 24 and converts a signal expressingthe phase of the VCO signal into a frequency signal.

The digital subtracter 26 detects a difference of an output signal ofthe digital differentiator 25 and the frequency setting code signal FCWand generates a frequency error signal. The loop gain control unit 27generates the digital control signal D_(ctl), on the basis of an outputsignal of the digital subtracter 26.

The digital control loop unit 3 is composed of an all-digital (AD) PLL.The description of an operation principle of the ADPLL is omitted. If afrequency of the reference signal is set as F_(ref), a setting frequencyF_(VCO) in the digital control loop unit 3 is represented by thefollowing formula (1).

F _(VCO) =FCW×F _(ref)   (1)

In the receiver 1 of FIG. 1, channel selection is performed by matchingthe setting frequency F_(VCO) represented by the formula (1) with acarrier frequency of the reception signal. However, if the receptionsignal is BPSK-modulated, a phase thereof is shifted by ±π/2. Therefore,inconsistency occurs between control operations of the analog controlloop unit 2 that tries to track the shifted phase and the digitalcontrol loop unit 3 that tries to maintain the phase within the constantrange. Therefore, the receiver 1 of FIG. 1 sets loop gain of the digitalcontrol loop unit 3 to be sufficiently higher than loop gain of theanalog control loop unit 2. As a result, the receiver 1 of FIG. 1demodulates and converts digitally a PSK modulation signal, therebyimproving resistance to an interfering wave superimposed on a modulationsignal.

FIGS. 2A and 2B are diagrams illustrating a demodulation principle of aBPSK signal. If the BPSK-modulated reception signal (BPSK signal) andthe VCO signal are input to the frequency converter 12, an output signalof the frequency converter 12 has two phases shown by circles of FIG.2A. That is, as illustrated in a timing diagram of FIG. 2B, because aphase of the VCO signal is delayed by π/2 as compared with a phase ofthe reception signal, the analog control loop unit 2 drives the analogcontrol signal V_(MIX) with a plus side and if the phase advances byπ/2, the analog control loop unit 2 drives the analog control signalV_(MIX) with a minus side and controls the phase to track the phase ofthe reception signal Data.

Meanwhile, the digital control loop unit 3 performs an operation forhindering an operation of the analog control loop unit 2. Because thegain of the digital control loop unit 3 is higher than the gain of theanalog control loop unit 2, a phase of the digital control signalD_(ctl) becomes a phase opposite to the phase of the analog controlsignal V_(MIX), as illustrated in FIG. 2B. As a result, the analogcontrol signal V_(MIX) and the digital control signal D_(ctl) becomedifferential signals of which phases are opposite to each other. If thephase when the digital control signal D_(ctl) is operated with the plusside is determined as 1(+π/2) and the phase when the digital controlsignal D_(ctl) is operated with the minus side is determined as 0(−π/2),the BPSK signal can be demodulated.

The digital control signal D_(ctl) generated by the loop gain controlunit 27 of FIG. 1 has a value converted digitally and if the data slicer5 is provided, binary data of 0 and 1 can be generated easily. Asillustrated in FIG. 3, the data slicer 5 is a digital comparatoroperated with a reference clock synchronized with a symbol rate of thereception signal and determination of 1(+π/2) and 0(−π/2) can beperformed accurately by setting a threshold value to an appropriatelevel.

As such, in the receiver 1 of FIG. 1, an A/D converter that needs to beprovided originally at a rear step side of the frequency converter 12 isunnecessary because digital conversion is performed by the phase-digitalconverter 22 in the digital control loop unit 3 and an internalconfiguration can be simplified.

In addition, according to a maximum characteristic of the receiver 1 ofFIG. 1, resistance to the interfering wave is remarkably high ascompared with an analog synchronous FSK/PSK receiver 1 according to therelated art. If the loop gain of the digital control loop unit 3 is setto be higher than the loop gain of the analog control loop unit 2, thevoltage controlled oscillator 4 can be prevented from being pulled in aninterfering wave frequency, even though an interfering wave having largepower exists.

Because the loop gain of the digital control loop unit 3 is high at alow frequency (carrier frequency) side and is low at a high frequency(interfering wave frequency) side, an unnecessary component by theinterfering wave can be suppressed by a gain difference.

In addition, in the receiver 1 of FIG. 1, it is possible to generate adata signal digitally demodulated by the data slicer 5. Because thedigital demodulator does not need to be provided individually, aninternal configuration of the receiver 1 can be simplified.

Second Embodiment

In a second embodiment described below, a filter to suppress aninterfering wave is provided in a digital control loop unit (digitalcontrol loop circuitry) 3.

FIG. 4 is a block diagram illustrating a schematic configuration of areceiver 1 in a wireless communication device according to the secondembodiment of the present invention. In FIG. 4, components common to thecomponents of FIG. 1 are denoted with the same reference numerals and adifference is mainly described below.

The receiver 1 of FIG. 4 includes the digital control loop unit 3 thatis partially different from the digital control loop unit of FIG. 1. Aninternal configuration of an analog control loop unit (analog controlloop circuitry) 2 of FIG. 4 is the same as the analog control loop unit2 of FIG. 1.

The digital control loop unit 3 of FIG. 4 includes an integrator 28, aloop filter 29, and a channel selection filter 30 in addition to theconfiguration of the digital control loop unit 3 of FIG. 1. Theintegrator 28 converts a frequency error signal generated by a digitalsubtracter 26 into a phase error signal. The phase error signal is inputto a loop gain control unit (loop gain controller) 27.

The loop gain control unit 27 is configured by connecting a proportionalpath of gain α and an integral path of gain β. Thereby, the digitalcontrol loop unit 3 is operated as an ADPLL of a type II with two originpoles and one zero point. Loop gain of the ADPLL of the type II isattenuated at a secondary inclination (40 dB/dec) at a high frequencyside.

The loop filter 29 removes a frequency component higher than a frequencycomponent of a reception signal, performs smoothing, and generates adigital control signal D_(ctl).

The channel selection filter 30 is connected to a rear step of the loopfilter 29 and suppresses an interfering wave component included in thedigital control signal D_(ctl). The suppressed interfering wavecomponent is mainly an interfering wave component in the vicinity of achannel selection frequency.

If frequencies and amplitudes of a reception signal, a VCO signal, andan interfering wave signal at an input terminal of a frequency converter12 are set as ω_(RF), ω_(VCO), ω_(Blk), A_(RF), A_(VCO), and A_(Blk),respectively, an output V_(MIX) thereof is represented by the following(2), by multiplication processing of the frequency converter 12. Aduplicate wave component generated by multiplication is ignored inconsideration of the following filter processing.

$\begin{matrix}\begin{matrix}{V_{MIX} = {\left\{ {{A_{RF}{\cos\left( {{\omega_{RF}t} + \phi_{m}} \right\}}} + {A_{Blk}{\cos \left( {\omega_{Blk}t} \right)}}} \right\} \times A_{VCO}{\cos \left( {\omega_{VCO}t} \right)}}} \\{= {{\left( {A_{RF}{A_{VCO}/2}} \right){\cos \left( {{\omega_{RF}t} - {\omega_{VCO}t} + \phi_{m}} \right)}} +}} \\{{\left( {A_{Blk}{A_{VCO}/2}} \right){\cos \left( {{\omega_{Blk}t} - {\omega_{VCO}t}} \right)}}} \\{= {{\left( {A_{RF}{A_{VCO}/2}} \right){\cos \left( \phi_{m} \right)}} + {\left( {A_{Blk}{A_{VCO}/2}} \right)\cos \left\{ {\left( {\omega_{Blk} - \omega_{VCO}} \right)t} \right\}}}}\end{matrix} & (2)\end{matrix}$

Therefore, in the case of BPSK modulation, because φ_(m)=±/π issatisfied, a first term of a right side of the formula (2) becomes asignal component that takes a value of ±(A_(RF)A_(VCO)/2) and is to bedemodulated. A second term of the right side becomes an unnecessarycomponent by an interfering wave. The unnecessary component appears in adifference frequency of the VCO signal and the interfering wave. Forexample, when a frequency of the VCO signal is 2.4 GHz and a frequencyof the interfering wave is 2.403 GHz, the unnecessary component of thesecond term of the second formula (2) appears at 3 MHz.

In the wireless communication, power of the interfering wave is largerthan power of a desired reception signal and if the reception signal isdemodulated as it is, an error rate may be greatly deteriorated. FIGS.5A to FIG. 5D are timing diagrams illustrating an example of thecorresponding case. FIG. 5A is a diagram illustrating data included in areception signal, FIG. 5B is a diagram illustrating an analog controlsignal V_(MIX) of an analog control loop, FIG. 5C is a diagramillustrating a digital control signal D_(ctl) of a digital control loop,and FIG. 5D is a diagram illustrating a waveform of an output signalD′_(ctl) of the channel selection filter 30.

The unnecessary component is superimposed on both the analog controlsignal V_(MIX) of FIG. 5B and the digital control signal D_(ctl) of FIG.5C. If the digital control signal D_(ctl) is input to the data slicer 5,1 and 0 cannot be determined accurately. Meanwhile, in the output signalD′_(ctl) of the channel selection filter 30, as illustrated in FIG. 5D,the interfering wave is suppressed. If the output signal D′_(ctl) isinput to the data slicer 5, 1 and 0 can be determined accurately by thedata slicer 5.

Because an input signal of each of the loop filter 29 and the channelselection filter 30 according to this embodiment is a digital signal,each of the loop filter 29 and the channel selection filter 30 can beconfigured using a complete digital circuit. More specifically, each ofthe loop filter 29 and the channel selection filter 30 can be configuredusing an IIR filter or an FIR filter.

FIG. 6 is a block diagram illustrating an example of the IIR filter andFIG. 7 is a block diagram illustrating an example of the FIR FILTER.These block diagrams are exemplary and various changes can be made.

In the channel selection filter 30, the IIR filter and the FIR filterare preferably combined appropriately according to a specification of arequired group delay characteristic. However, the loop filter 29 isincluded in the digital control loop composed of ADPLL. Therefore, ifstability of the loop is considered, the channel selection filter 30 ispreferably composed of the IIR filter having a small delay amount.

As such, in the second embodiment, because the loop filter 29 and thechannel selection filter 30 are provided at the rear step of the loopgain control unit 27, the unnecessary component superimposed on thedigital control signal D_(ctl) generated by the digital control loopunit 3 can be removed and an error rate at the time of reception can bereduced.

In addition, in this embodiment, because the channel selection filter 30of the digital type is provided, an area and consumption power of thereceiver 1 can be reduced as compared with the channel selection filter30 of the analog type is provided. Because the loop filter 29 and thechannel selection filter 30 can be configured using the IIR filter andthe FIR filter illustrated in FIGS. 6 and 7, a configuration can besimplified and the receiver 1 can be easily designed.

Third Embodiment

In a third embodiment described below, a function of cancelling afrequency offset of a reception signal and a VCO signal is provided.

FIG. 8 is a block diagram illustrating a schematic configuration of areceiver 1 in a wireless communication device according to the thirdembodiment of the present invention. In FIG. 8, components common to thecomponents of FIGS. 1 and 4 are denoted with the same reference numeralsand a difference is mainly described below.

The receiver 1 of FIG. 8 includes a digital control loop unit (digitalcontrol loop circuitry) 3 having a configuration that is partiallydifferent from the configurations of the digital control loop units ofFIGS. 1 and 4. An internal configuration of an analog control loop unit(analog control loop circuitry) 2 of FIG. 8 is the same as the analogcontrol loop unit 2 of FIG. 1.

The digital control loop unit 3 of FIG. 8 includes a frequency offsetcancellation unit (frequency offset cancellation circuitry) 31 inaddition to the configuration of the digital control loop unit 3 of FIG.4. The frequency offset cancellation unit 31 performs processing forcancelling a deviation (offset) of a frequency of the reception signaland a frequency of the VCO signal.

As illustrated in FIG. 8, the frequency offset cancellation unit 31 hasa differentiator 32 to perform differentiation processing of an outputsignal of a channel selection filter 30, an adder 33, a gain controlunit (gain controller) 34, and an integrator 35.

In normal wireless communication, because reference signal sources of atransmitter and the receiver 1 are different from each other,frequencies of the individual reference signal sources are deviated by aminute amount of several to several ten ppm. If there is a frequencyoffset between the reception signal and the VCO signal, an output signalof the frequency converter 12 includes a phase error that increasesaccording to a time.

FIGS. 9A to 9C are timing diagrams when there is the frequency offsetbetween the reception signal and the VCO signal. FIG. 9A is a diagramillustrating data included in the reception signal, FIG. 9B is a diagramillustrating an analog control signal V_(MIX), and FIG. 9C is a diagramillustrating a waveform of a digital control signal D_(ctl). If there isthe frequency offset, as illustrated in FIG. 9B, a signal level of theanalog control signal V_(MIX) gradually increases and diverges and asignal level of the digital control signal D_(ctl) in a differentialrelation gradually decreases and diverges. Therefore, the digitalcontrol signal D_(ctl) is smaller than a threshold value and 0 and 1cannot be detected accurately by a data slicer 5.

The frequency offset cancellation unit 31 corrects a frequency settingcode signal FCW using a preamble portion provided immediately before adata portion, for each of symbols included in the reception signal. Thepreamble portion includes a carrier signal that is not modulated and thedata portion includes a carrier signal that is modulated.

For example, in the case of a simple sine wave signal of a frequencyω_(RF) where the preamble portion is not BPSK-modulated, if thefrequency offset of the reception signal and the VCO signal is set asω_(os), a phase error accumulated for each cycle T_(REF) of a referencesignal is represented by the following formula (3).

Δφ=ω_(os) ×T _(REF)   (3)

FIG. 10A is a diagram illustrating data of the reception signal in thepreamble portion of the reception signal, FIG. 10B is a diagramillustrating the analog control signal V_(MIX) in the preamble portion,and FIG. 10C is a diagram illustrating a waveform of the digital controlsignal D_(ctl) in the preamble portion. FIG. 11 is a diagramillustrating a phase-voltage characteristic of the analog control signalV_(MIX).

As illustrated in FIG. 10C, if gain of the vicinity of an origin of thephase-voltage characteristic of the frequency converter 12 is set as A,a variation ΔV_(MIX) of a control voltage of the analog control loop bya phase error of the formula (3) described above is represented by thefollowing formula (4).

ΔV _(MIX) =A×Δφ=A×ω _(os) ×T _(REF)   (4)

Because the digital control signal D_(ctl) is in a differential relationwith the formula (4), an output D_(out) of the differentiator in thefrequency offset cancellation circuit is represented by the followingformula (5).

D _(out) =A×ω _(os) ×T _(REF)   (5)

As seen from the formula (5), a value proportional to the frequencyoffset can be detected as the output D_(out) of the differentiator. Inthe frequency offset cancellation unit 31, a negative feedback loopconfigured using a gain control unit (gain controller) and a digitalintegrator adjusts a frequency setting code signal FCW. The frequencyoffset cancellation unit 31 is a primary control system in which thenumber of origin poles by the digital integrator is one.

As such, in the third embodiment, the frequency offset cancellation unit31 is provided to cancel the frequency offset of the reception signaland the VCO signal. Therefore, the phase error is not accumulated in thedigital control signal D_(ctl) and an error rate can be suppressed atthe time of reception and demodulation.

Fourth Embodiment

In a fourth embodiment described below, a processing result by frequencyoffset cancellation in the third embodiment is reflected at a highspeed.

FIG. 12 is a block diagram illustrating a schematic configuration of areceiver 1 in a wireless communication device according to the fourthembodiment. In FIG. 12, components common to the components of FIG. 8are denoted with the same reference numerals and a difference is mainlydescribed below.

The receiver 1 of FIG. 12 is obtained by newly providing a high-speedsettling gain control unit (first high-speed settling gain controller)41 in the digital control loop unit 3 of FIG. 8 and the otherconfiguration thereof is the same as the configuration of the receiver 1of FIG. 8.

The high-speed settling gain control unit 41 multiplies an output signalof a frequency offset cancellation unit (frequency offset cancellationcircuitry) 31 by γ and performs gain adjustment. An output signal of thehigh-speed settling gain control unit 41 is added to an output signal ofa loop filter 29 by a digital adder 42 and a final digital controlsignal D_(ctl) is generated.

As such, in a digital control loop unit (digital control loop circuitry)3 of FIG. 12, the output signal of the frequency offset cancellationunit 31 is used to correct a frequency setting code signal FCW and isused to correct the digital control signal D_(ctl) output from the loopfilter 29. The reason is as follows. A transfer function of a signal ona path reaching from an input of the frequency setting code signal FCWin the data control loop to a voltage controlled oscillator 4 has acharacteristic of a low-pass filter determined by a loop band of thedigital control loop unit 3, as shown by a waveform w1 of FIG. 13.Therefore, a time corresponding to a response time determined by thetransfer function may be necessary for cancelling the frequency offset,whenever the frequency offset cancellation unit 31 corrects a value ofthe frequency setting code signal FCW. That is, the loop band of thefrequency offset cancellation unit 31 may be restricted.

Meanwhile, a transfer function of a signal on a path reaching from anoutput of the loop filter 29 to an input of the voltage controlledoscillator 4 has a characteristic of a high-pass filter, as shown by awaveform w2 of FIG. 13. When the transfer function has thecharacteristic of the high-pass filter, it means that, if the outputsignal of the frequency offset cancellation unit 31 is superimposed onthe path, an effect of the frequency offset can be reflected quickly.

Therefore, in this embodiment, the gain of the output signal of thefrequency offset cancellation unit 31 is adjusted by the high-speedsettling gain control unit 41 composed of a digital multiplier, theoutput signal of the frequency offset cancellation unit 31 issynthesized with the output signal of the loop filter 29, and the effectof the frequency offset appears quickly.

As such, in the fourth embodiment, because the output signal of thefrequency offset cancellation unit 31 is synthesized with the outputsignal of the loop filter 29 having the characteristic of the high-passfilter, the frequency offset can be adjusted quickly.

Fifth Embodiment

A fifth embodiment described below can be used when an FSK-modulatedsignal is received.

FIG. 14 is a block diagram illustrating a schematic configuration of areceiver 1 in a wireless communication device according to the fifthembodiment. In FIG. 14, components common to the components of FIG. 4are denoted with the same reference numerals and a difference is mainlydescribed below.

The receiver 1 of FIG. 14 includes a phase shift unit (phase shiftcircuitry) 51 and an adder (adder circuitry) 52 provided in a digitalcontrol loop unit (digital control loop circuitry) 3, in addition to theconfiguration of FIG. 4. The phase shift unit 51 prevents accumulationof a phase error. An output signal of the phase shift unit 51 is addedto an output of an integrator 28 by the adder 52 and is input to a loopgain control unit (loop gain controller) 27.

In the case in which the PSK-modulated signal is received, if afrequency offset of the reception signal and a VCO signal is corrected,the phase error is not accumulated and an analog control signal V_(MIX)and a digital control signal D_(ctl) do not diverge. However, in thecase of FSK modulation, if 1 (reception signal frequency isω_(RF)+Δω_(m)) appears continuously as data or 0 (reception signalfrequency is ω_(RF)−Δω_(m)) appears continuously as the data, the phaseerror may be accumulated and the analog control signal V_(MIX) and thedigital control signal D_(ctl) may diverge. The phase shift unit 51prevents the accumulation and the divergence.

FIGS. 15A and 15B are waveform diagrams illustrating an operationprinciple of the phase shift unit 51. FIG. 15A illustrates the case inwhich the phase shift unit 51 is not provided and FIG. 15B illustratesthe case in which the phase shift unit 51 is provided. For example, whendata received in the reception signal is 111, a phase of a waveform w2of the digital control signal D_(ctl) becomes opposite to a phase of awaveform w1 of the analog control signal V_(MIX). Therefore, a value ofthe digital control signal D_(ctl) becomes 100 and the value isdifferent from a value of the data of the reception signal, from asecond symbol of the data.

Therefore, the phase shift unit 51 shifts the phase of the digitalcontrol signal D_(ctl) in accordance with output data of a data slicer5, for each symbol. For example, if output data of the data slicer 5 is1, the phase of the digital control signal D_(ctl) is shifted by +π/2and if the output data of the data slicer 5 is 0, the phase of thedigital control signal D_(ctl) is shifted by −π/2. Thereby, when thedata 111 is included in the reception signal, as illustrated in FIG.15B, the phase shift unit 51 shifts the phase of the digital controlsignal D_(ctl) by +π/2, for each symbol. As a result, the data 111 isoutput from the data slicer 5.

As such, in the fifth embodiment, when the FSK-modulated signal isreceived, the phase of the digital control signal D_(ctl) is shifted bythe phase shift unit 51, in accordance with the output data of the dataslicer 5. Therefore, even when data having the same value appearscontinuously in the reception signal, the phase error is not accumulatedand the signal can be demodulated accurately.

The digital control loop unit 3 of FIG. 14 has the loop filter 29 andthe channel selection filter 30. However, at least one of the loopfilter 29 and the channel selection filter 30 may be omitted.

Sixth Embodiment

In a sixth embodiment described below, a function of cancelling a phaseoffset is provided.

FIG. 16 is a block diagram illustrating a schematic configuration of areceiver 1 in a wireless communication device according to the sixthembodiment. In FIG. 16, components common to the components of FIG. 14are denoted with the same reference numerals and a difference is mainlydescribed below.

The receiver 1 of FIG. 16 includes a phase offset cancellation unit(phase offset cancellation circuitry) 53 and an adder 54 provided in adigital control loop unit (digital control loop circuitry) 3, inaddition to the configuration of FIG. 14. The phase offset cancellationunit 53 detects a phase difference at a phase having superior linearity,when the phase difference is detected by a frequency converter 12. Anoutput signal of the phase offset cancellation unit 53 is added to anoutput signal of the integrator 28 by the adder 54 and is input to theadder 52.

That is, in the first to fifth embodiments described above, data isdemodulated in a state in which a phase difference of the receptionsignal and the VCO signal is zero and linearity of a phase-voltagecharacteristic of the frequency converter 12 is best. However, asillustrated in FIG. 17, there is the case in which the demodulationneeds to be performed in a state in which a phase difference having badlinearity is set as an initial value. Therefore, the phase offsetcancellation unit 53 performs process for returning the initial value toan optimal value.

The phase offset cancellation unit 53 performs phase offset cancellationprocessing using a preamble portion provided for each of symbols of thereception signal. It is assumed that ω_(RF) of the reception signal andω_(VCO) of the VCO signal are matched with each other. In this state,the phase offset cancellation unit 53 stores a digital control signalD_(ctl) and an inclination while sweeping a phase of the VCO signal from0 to 2π, with resolution of about π/8, for example. As a result, asillustrated in FIG. 17, the digital control signal D_(ctl) changes whiletaking a maximum and a minimum value alternately and an optimal phasestate is obtained when the inclination becomes minus in an intermediatevalue of the maximum value and the minimum value.

As such, in the sixth embodiment, because the phase offset cancellationunit 53 is provided in the digital control loop unit 3, datademodulation can be performed in a phase state in which the linearity ofdigital control signal D_(ctl) is good and demodulation processing isperformed without being affected by the phase offset of the receptionsignal and the VCO signal.

The digital control loop unit 3 of FIG. 16 has the phase shift unit 51and the phase offset cancellation unit 53. However, the phase shift unit51 may be omitted. In addition, at least one of the loop filter 29 andthe channel selection filter 30 may be omitted.

Seventh Embodiment

A seventh embodiment described below includes all of the characteristicconfigurations of the first to sixth embodiments described above.

FIG. 18 is a block diagram illustrating a schematic configuration of areceiver 1 in a wireless communication device according to the seventhembodiment. The receiver 1 of FIG. 18 includes a high-speed settlinggain control unit (second high-speed settling gain controller) 56 for aphase shift unit (phase shift circuitry) 51 and a high-speed settlinggain control unit (third high-speed settling gain controller) 59 for aphase offset cancellation unit 53, in addition to a high-speed settlinggain control unit (first high-speed settling gain controller) 41 for afrequency offset cancellation unit (frequency offset cancellationcircuitry) 31, similar to FIG. 12.

A digital differentiator 57 is provided at a rear step of the high-speedsettling gain control unit 56 for the phase shift unit 51. Likewise, adigital differentiator 60 is provided at a rear step of the high-speedsettling gain control unit 59 for the phase offset cancellation unit 53.

An output signal of the high-speed settling gain control unit 41 for thefrequency offset cancellation unit 31 and an output signal of thedigital differentiator 57 are synthesized by a digital adder 58. Anoutput signal of the digital adder 58 and an output signal of thedigital differentiator 60 are synthesized by a digital adder 61. Anoutput signal of the digital adder 61 and an output signal of a loopfilter 29 are synthesized by a digital adder 62 and a final digitalcontrol signal D_(ctl) is generated. The digital control signal D_(ctl)is a signal used in consideration of cancellation of the frequencyoffset, accumulation prevention of a phase error, and cancellation ofthe phase offset and the digital control signal is synthesized by adigital adder 24 on a path having a characteristic of a high-passfilter. Therefore, the cancellation of the frequency offset, theaccumulation prevention of a phase error, and the cancellation of thephase offset can be performed at a high speed.

Eighth Embodiment

In the first to seventh embodiments described above, the configurationand operation of the receiver 1 are described. However, in an eighthembodiment described below, in addition to the configuration of thereceiver 1 according to any one of the first to seventh embodiments, ahardware configuration example of a wireless communication deviceincluding a transmitter will be described. Because a receiver 1 in thewireless communication device according to the eighth embodiment has theconfiguration according to any one of the first to seventh embodiments,detailed description thereof is omitted.

FIG. 19 is a block diagram illustrating a schematic configuration of awireless communication device 71 according to the eighth embodiment. Thewireless communication device 71 of FIG. 19 includes a baseband unit(baseband circuitry) 72, an RF unit (RF circuitry) 73, and an antennaunit (antenna circuitry) 74.

The baseband unit 72 has a control circuit 75, a transmission processingcircuit 76, and a reception processing circuit 77. Each circuit in thebaseband unit 72 performs digital signal processing.

The control circuit 75 performs processing of a media access control(MAC) layer, for example. The control circuit 75 may perform processingof a network hierarchy upper than the MAC layer. In addition, thecontrol circuit 75 may perform processing multi-input multi-output(MIMO). For example, the control circuit 75 may perform propagation pathestimation processing, transmission weight calculation processing, andstream separation processing.

The transmission processing circuit 76 generates a digital transmissionsignal. The reception processing circuit 77 performs processing such asanalysis of a preamble and a physical header, after executing digitaldemodulation or decoding.

The RF unit 73 has a transmission circuit 78 and a reception circuit 79.The transmission circuit 78 includes a transmission filter (notillustrated in the drawings) to extract a signal of a transmission band,a mixer (not illustrated in the drawings) to up-convert a signal havingpassed through the transmission filter into a radio frequency using anoscillation signal of a VCO 4, and a preamplifier. The reception circuit79 has the same configuration as the configuration of the receiver 1according to any one of the first to seventh embodiments. That is, thereception circuit 79 has a TDC 22, an ADPLL unit (ADPLL circuitry) 80, areception RF unit (reception RF circuitry) 81, and a VCO 4. The ADPLLunit 80 has a binary counter 23, a digital adder 24, a digitaldifferentiator 25, a digital subtracter 26, and a loop gain control unit(loop gain controller) 27 of FIG. 1, for example. The reception RF unit81 has a low noise amplifier 11, a frequency converter 12, and alow-pass filter 13 of FIG. 1, for example. In the RF unit 73 of FIG. 19,the VCO 4 is used commonly in the transmission circuit 78 and thereception circuit 79. However, the VCO may be provided in each of thetransmission circuit 78 and the reception circuit 79.

When the radio signal is transmitted and received by the antenna unit74, a switch to connect any one of the transmission circuit 78 and thereception circuit 79 to the antenna unit 74 may be provided in the RFunit 73. If the switch is provided, the antenna unit 74 can be connectedto the transmission circuit 78 at the time of transmission and theantenna unit 74 can be connected to the reception circuit 79 at the timeof reception.

The transmission processing circuit 76 of FIG. 19 outputs only atransmission signal of one system. However, a signal may be divided intoan I signal and a Q signal and the I signal and the Q signal may beoutput, according to a communication system. In this case, a blockconfiguration of the wireless communication device 71 is as illustratedin FIG. 20, for example. In the wireless communication device 71 of FIG.20, a configuration from the transmission processing circuit 76 to thetransmission circuit 78 is different from the configuration of FIG. 19.

The transmission processing circuit 76 generates digital basebandsignals (hereinafter, referred to as a digital I signal and a digital Qsignal) of two systems.

A DA conversion circuit 82 to convert the digital I signal into ananalog I signal and a DA conversion circuit 83 to convert the digital Qsignal into an analog Q signal are provided between the transmissionprocessing circuit 76 and the transmission circuit 78. The transmissioncircuit 78 up-converts the analog I signal and the analog Q signal bythe mixer not illustrated in the drawings.

The RF unit 73 and the baseband unit 72 illustrated in FIGS. 19 and 20may be configured using an integrated circuitry of one chip and the RFunit 73 and the baseband unit 72 may be configured using an integratedcircuitry of different chips. In addition, parts of the RF unit 73 andthe baseband unit 72 may be configured by discrete components and theremaining portions may be configured using a plurality of chips.

In addition, the RF unit 73 and the baseband unit 72 may be configuredusing a software radio that can be reconfigured in a software manner. Inthis case, functions of the RF unit 73 and the baseband unit 72 may berealized in a software manner using a digital signal processingprocessor. In this case, a bus, a processor core, and an externalinterface unit (external interface circuitry) are provided in thewireless communication device 71 illustrated in FIGS. 19 and 20. Theprocessor core and the external interface unit are connected via the busand firmware is operated in the processor core. The firmware can beupdated by a computer program. The processor core operates the firmware,so that processing operations of the RF unit 73 and the baseband unit 72illustrated in FIGS. 19 and 20 can be executed by the processor core.

The wireless communication device 71 illustrated in FIGS. 19 and 20includes only one antenna unit (antenna circuitry) 74. However, thenumber of antennas is not limited in particular. The antenna unit 74 fortransmission and the antenna unit 74 for reception may be providedindividually and the antenna unit 74 for the I signal and the antennaunit 74 for the Q signal may be provided individually. When only oneantenna unit 74 is provided, the transmission and the reception may beswitched by a transmission/reception switch.

The wireless communication device 71 illustrated in FIGS. 19 and 20 canbe applied to a stationary wireless communication device 71 such as anaccess point, a wireless router, and a computer, can be applied to aportable wireless terminal such as a smartphone and a mobile phone, canbe applied to a peripheral device, such as a mouse and a keyboard,performing wireless communication with a host device, and can be appliedto a wearable terminal communicating biological information wirelessly.A wireless system of wireless communication between the wirelesscommunication devices 71 illustrated in FIGS. 19 and 20 is not limitedin particular and various communication systems such as cellularcommunication after the third generation, wireless LAN, Bluetooth(registered trademark), and proximity wireless communication can beapplied.

FIG. 21 illustrates an example of the case in which wirelesscommunication is performed between a PC 84 as a host device and a mouse85 as a peripheral device. The wireless communication device 71illustrated in FIG. 19 or 20 is embedded in both the PC 84 and the mouse85. The mouse 85 performs wireless communication using power of anembedded battery. However, because a space to embed the battery islimited, the wireless communication needs to be performed using minimumconsumption power. Therefore, the wireless communication is preferablyperformed using a wireless system enabling low consumption powerwireless communication such as Bluetooth Low Energy formulated in astandard of Bluetooth (registered trademark) 4.0.

FIG. 22 illustrates an example of the case in which the wirelesscommunication is performed between a wearable terminal 86 and a hostdevice (for example, the PC 84). The wearable terminal 86 is mounted ona human body. In addition to a type of being mounted on an arm asillustrated in FIG. 22, various types such as a sealing type of beingstuck on the human body, a glass type and an earphone type of beingmounted on the human body other than the arm, and a type of beinginserted into the human body like a pacemaker are considered. In thecase of FIG. 22, the wireless communication device 71 illustrated inFIG. 19 or 20 is embedded in both the wearable terminal 86 and the PC84. The PC 84 is a computer or a server. Because the wearable terminal86 is attached to the human body, a space for an embedded battery islimited. Therefore, the wireless system enabling the low consumptionpower wireless communication such as Bluetooth Low Energy is preferablyadopted.

In addition, when the wireless communication is performed between thewireless communication devices 71 illustrated in FIGS. 19 and 20, a typeof information transmitted and received by the wireless communication isnot limited in particular. However, when information having a large dataamount such as moving image data is transmitted and received and wheninformation a small data amount such as operation information of themouse 85 is transmitted and received, a wireless system is preferablychanged and the wireless communication needs to be performed using anoptimal wireless system, according to an amount of informationtransmitted and received.

In addition, when the wireless communication is performed between thewireless communication devices 71 illustrated in FIGS. 19 and 20, aninforming unit (informing circuitry) to inform a user of an operationstate of the wireless communication may be provided. As a specificexample of the informing unit, the informing unit may display theoperation state on a display device such as an LED, the informing unitmay inform the user of the operation state using vibration of avibrator, and the informing unit may inform the user of the operationstate using audio information by a speaker or a buzzer.

At least a part of the receiver 1 described in the embodiments may beconfigured by hardware and may be configured by software. When at leastthe part of the receiver 1 is configured by the software, a program forrealizing a function of at least the part of the receiver 1 may bestored in a recording medium such as a flexible disk and a CD-ROM andmay be read and performed by a computer. The recording medium is notlimited to a removable recording medium such as a magnetic disk and anoptical disk and may be a stationary recording medium such as a harddisk device and a memory.

The program for realizing the function of at least the part of thereceiver 1 may be distributed through a communication line (includingthe wireless communication) such as the Internet. In addition, the sameprogram may be encrypted or modulated and may be distributed in acompressed state through a wired circuit or a wireless circuit such asthe Internet or the same program may be stored in the recording mediumand may be distributed.

While certain embodiments have been described, these embodiments havebeen presented by way of example only, and are not intended to limit thescope of the inventions. Indeed, the novel methods and systems describedherein may be embodied in a variety of other forms; furthermore, variousomissions, substitutions and changes in the form of the methods andsystems described herein may be made without departing from the spiritof the inventions. The accompanying claims and their equivalents areintended to cover such forms or modifications as would fall within thescope and spirit of the inventions.

1. A wireless communication device comprising: an analog control loopcircuitry that generates an analog control signal to adjust a phase of avoltage controlled oscillation signal, in accordance with a phase of areception signal; a digital control loop circuitry that generates adigital control signal having a frequency determined by a frequency of areference signal and a predetermined frequency setting code signal andhaving a phase opposite to a phase of the analog control signal; avoltage controlled oscillator that generates the voltage controlledoscillation signal, on the basis of the analog control signal and thedigital control signal; and a data slicer that generates a digitalsignal obtained by digital demodulation of the reception signal, on thebasis of a comparison result of the digital control signal and apredetermined threshold value, wherein gain of the digital control loopcircuitry is higher than gain of the analog control loop circuitry. 2.The wireless communication device according to claim 1, wherein theanalog control loop circuitry comprises a frequency converter thatgenerates a phase difference signal of the reception signal and thevoltage controlled oscillation signal and a low-pass filter thatrestricts a band of an output signal of the frequency converter andgenerates the analog control signal, and the digital control loopcircuitry has a phase-digital converter that detects a phase of thevoltage controlled oscillation signal in synchronization with thereference signal, a digital differentiator that performs differentiationprocessing on an output signal of the phase-digital converter andconverts the output signal into frequency information, a digitalsubtracter that detects a difference of an output signal of the digitaldifferentiator and the frequency setting code signal and generates afrequency error signal, and a loop gain controller that generates thedigital control signal, on the basis of an output signal of the digitalsubtracter.
 3. The wireless communication device according to claim 2,further comprising: a first filter that smooths an output signal of theloop gain controller and generates the digital control signal; and asecond filter that supplies a signal obtained by removing an interferingwave component included in an output signal of the first filter to thedata slicer, wherein the data slicer generates the digital signal, onthe basis of a comparison result of an output signal of the secondfilter and the predetermined threshold value.
 4. The wirelesscommunication device according to claim 2, further comprising: afrequency offset cancellation circuitry that corrects the frequencysetting code signal to eliminate an error of a frequency of thereception signal and a frequency of the voltage controlled oscillationsignal.
 5. The wireless communication device according to claim 4,wherein the reception signal includes a preamble portion including anon-modulated carrier signal and a modulation portion obtained bymodulating data in the carrier signal, for each symbol, and thefrequency offset cancellation circuitry corrects the frequency settingcode signal on the basis of the preamble portion of the receptionsignal, for each symbol.
 6. The wireless communication device accordingto claim 4, further comprising: a first high-speed settling gaincontroller that adjusts the digital control signal output from the loopgain controller, on the basis of a correction signal that corrects thefrequency setting code signal by the frequency offset cancellationcircuitry, wherein the digital control signal corrected by the firsthigh-speed settling gain controller is input to the voltage controlledoscillator.
 7. The wireless communication device according to claim 2,wherein the reception signal is a frequency-shift keying (FSK) signal,and the wireless communication device further includes a phase shiftcircuitry that adjusts a phase of an output signal of the digitalsubtracter, on the basis of the digital signal generated by the dataslicer, such that a phase of the digital control signal changes in amonotonic increase direction or a monotonic decrease direction for eachsymbol.
 8. The wireless communication device according to claim 7,further comprising: a second high-speed settling gain controller thatadjusts the digital control signal output from the loop gain controller,on the basis of a phase adjustment signal to adjust the phase of theoutput signal of the digital subtracter by the phase shift circuitry. 9.The wireless communication device according to claim 2, furthercomprising: a phase offset cancellation circuitry that adjusts a phaseof the digital control signal, in accordance with timing when the analogcontrol signal becomes equal to an intermediate value of a maximumamplitude value and a minimum amplitude value, when a frequency of theanalog control signal and a frequency of the digital control signal arematched with each other.
 10. The wireless communication device accordingto claim 9, further comprising: a third high-speed setting gaincontroller that adjusts the digital control signal output from the loopgain controller, on the basis of a phase adjustment signal that adjuststhe phase of the digital control signal by the phase offset cancellationcircuitry.
 11. The wireless communication device according to claim 9,wherein the reception signal is a frequency-shift keying (FSK) signalthat includes a preamble portion including a non-modulated carriersignal and a modulation portion obtained by modulating data in thecarrier signal, for each symbol, and the phase offset cancellationcircuitry adjusts the phase of the digital control signal using thecarrier signal in the preamble portion.
 12. A wireless communicationdevice comprising: an RF circuitry; and a baseband circuitry, whereinthe RF circuitry has a transmission circuitry and a reception circuitry,the baseband circuitry has a transmission processing circuitry and areception processing circuitry, the reception circuitry has an analogcontrol loop circuitry that generates an analog control signal to adjusta phase of a voltage controlled oscillation signal, in accordance with aphase of a reception signal, a digital control loop circuitry thatgenerates a digital control signal having a frequency determined by afrequency of a reference signal and a predetermined frequency settingcode signal and having a phase opposite to a phase of the analog controlsignal, and a voltage controlled oscillator that generates the voltagecontrolled oscillation signal, on the basis of the analog control signaland the digital control signal, the reception processing circuitry has adata slicer that generates a digital signal obtained by performingdigital demodulation on the reception signal, on the basis of acomparison result of the digital control signal and a predeterminedthreshold value, and gain of the digital control loop circuitry ishigher than gain of the analog control loop circuitry.
 13. An integratedcircuitry comprising the wireless communication device according toclaim
 1. 14. A wireless communication device comprising: the integratedcircuitry according to claim 13; and at least one antenna.
 15. Awireless communication method comprising: generating an analog controlsignal that adjusts a phase of a voltage controlled oscillation signal,in accordance with a phase of a reception signal, using an analogcontrol loop circuitry; generating a digital control signal having afrequency determined by a frequency of a reference signal and apredetermined frequency setting code signal and having a phase oppositeto a phase of the analog control signal, using a digital control loopcircuitry; generating the voltage controlled oscillation signal, on thebasis of the analog control signal and the digital control signal; andgenerating a digital signal obtained by digital demodulation of thereception signal, on the basis of a comparison result of the digitalcontrol signal and a predetermined threshold value, wherein gain of thedigital control loop circuitry is higher than gain of the analog controlloop circuitry.